Signal receiving circuit and signal receiving method

ABSTRACT

A signal receiving circuit is provided which is capable of receiving sample data, even if a number of sample data to be transmitted from a transmitting terminal does not coincide with that of sample data to be received by a receiving terminal without an occurrence of discontinuity in received sample data.  
     The signal receiving circuit is provided with a converting circuit adapted to perform computations on a plurality of pieces of first sample data contained in n 1  pieces (n 1  is a natural number) of first sample data to be sequentially input and to sequentially produce, in response to a clock signal, n 2  pieces (n 2  is a natural number) of second sample data and with a receiving section adapted to sequentially receive the n 2  pieces of the second sample data in response to the clock signal.

BACKGROUND OF THE INVENTION

[0001] 1. Field of the Invention

[0002] The present intention relates to a signal receiving circuit and a method for receiving signals and more particularly to the signal receiving circuit and the method for receiving signals used for a receiving terminal carrying out communications with a transmitting terminal in an asynchronous manner.

[0003] The present application claims priority of Japanese Patent Application No.2000-059265 filed on Mar. 3, 2000, which is hereby incorporated by reference.

[0004] 2. Description of the Related Art

[0005] Digital communications for transmitting and receiving digital signals are widely used. In digital communications, in some cases, communications are carried out between terminals in asynchronous transmission, without using synchronous signals. Even in a case of asynchronous digital communications, it is desired that a receiving terminal receives signals at a same sampling frequency as is used when a transmitting terminal transmits signals. To achieve this, each of the transmitting and receiving terminals has a clock signal generating circuit adapted to generate a clock signal of a same frequency and a sampling is attempted at a same sampling frequency.

[0006] However, it is actually impossible that each of the transmitting and receiving terminals generates the clock signal of completely the same frequency and transmits and receives signal at completely the same sampling frequency. For example, when signals are transmitted and received at a sampling frequency of 16 kHz, a frequency difference of about 4 kHz occurs. This means that the number of pieces of sample data contained in a transmitting signal generated by the transmitting terminal differs, by 4 pieces per one second, from that of sample data that the receiving terminal is to receive.

[0007] When the number of pieces of the sample data contained in the transmitting signal generated by the transmitting terminal is different from the number of pieces of the sample data to be received by the receiving terminal, the receiving terminal uses a signal receiving circuit adapted to solve a problem of the difference in the number of pieces of data.

[0008] Such a signal receiving circuit is disclosed in Japanese Patent Application Laid-open No. Hei 8-32562, as shown in FIG. 7. A conventionally known signal receiving circuit 200 is used to receive a digital voice signal. As shown in FIG. 7, the signal receiving circuit 200 is provided with a digital voice input terminal 101. The digital voice input terminal 101 is connected to a buffer memory 102. Moreover, the signal receiving circuit 200 has a writing clock input terminal 103.

[0009] The writing clock input terminal 103 is connected to a writing address counter 104. The writing address counter 104 is connected to the buffer memory 102 and to a slip monitoring circuit 105. The signal receiving circuit 200 has further a reading clock input terminal 106. The reading clock input terminal 106 is connected to a reading address counter 107. The reading address counter 107 is connected to the buffer memory 102 and to the slip monitoring circuit 105. The buffer memory 102 is connected to a sound level calibrating circuit 108. The slip monitoring circuit 105 is connected to the sound level calibrating circuit 108. The sound level calibrating circuit 108 is connected to a digital voice output terminal 109.

[0010] Operations of the conventional signal receiving circuit 200 will be described. A digital voice input signal A input from the digital voice input terminal 101 is written into the buffer memory 102 sequentially, A writing clock signal B is input from the writing clock input terminal 103. The writing clock signal B is in sync with the digital voice input signal A. A writing address C is output from the writing address counter 104. Signal of the writing address is in sync with the writing clock signal B. The writing address is fed to the buffer memory 102. The digital voice input signal A is written in an address designated by the writing address C stored in the buffer memory 102.

[0011] A reading clock C is fed to the reading address counter 107 from the reading clock input terminal 105. A reading address E is output from the reading address counter 107. Signal of the reading address E is in sync with the reading clock D. The reading address E is fed to the buffer memory 102. The buffer memory 102 outputs a signal stored in an address designated by the reading address E as an output digital voice signal F to the sound level calibrating circuit 108.

[0012] The writing address C and the reading address E are input to the slip monitoring circuit 105. The slip monitoring circuit 105 monitors the writing address C and he reading address E at all times. The slip monitoring circuit 105, when a differential between the writing address C and reading address E comes close to a predetermined value, outputs a sound level control starting signal G to the sound level calibrating circuit 108. The sound level calibrating circuit 108 outputs the output digital voice signal F. The sound level calibrating circuit 108, by being triggered by the sound level control starting signal G, causes decay to occur in the amplitude of an output digital voice signal F′. The sound level calibrating circuit 108 minimizes the amplitude of the output digital voice signal F′ ten seconds after the sound level control starting signal G has been input.

[0013] The slip monitoring circuit 105, “t1” seconds after the amplitude of the output digital voice signal F′ has been minimized, that is, “t0+t1” seconds after the sound level control starting signal G has been input to the sound level calibrating circuit 108, outputs a reading address switching signal H to the reading address counter 107. The reading address E is switched in response to the reading address switching signal H. The output digital voice signal F1, “t1” seconds after the reading address E has been switched, is increased in amplitude gradually and is restored to its original level.

[0014] In the signal receiving circuit 200, if the writing clock signal B is not in sync with the signal of the reading address E, a dropout and/or overlap of data occurs. When the dropout and/or overlap of data occurs, the reading address E is switched. Before the reading address E is switched, the output digital voice signal F′ is gradually decreased in sound level.

[0015] After the reading address E has been switched, the sound level of the output digital voice signal F′ is gradually restored to its original one. When the reading address E has been switched, voice noise that has occurred due to the dropout and/or overlap of data are removed. In the conventional signal receiving circuit 200, no discontinuity in a signal waveform of the output digital voice signal F′ occurs.

[0016] In the conventional signal receiving circuit 200, if the dropout and/or overlap of data occurs, the amplitude of the output digital voice signal F′ is minimized for “t1” seconds. The output digital voice signal F′ has time when there is substantially no output for the “t1” seconds after the dropout and/or overlap has occurred. For example, when the output digital voice signal F′ is output via a speaker, the time when there is no sound occurs. The output digital voice signal F′ is discontinuous on a time axis.

[0017] It is desired that the discontinuity in the signal waveform contained in sample data to be received by the receiving terminal on the time axis is difficult to occur even when the number of pieces of sample data to be transmitted by the transmitting terminal does not coincide with that of sample data to be received by the receiving terminal.

SUMMARY OF THE INVENTION

[0018] In view of the above, it is an object of the present invention to provide a signal receiving circuit capable of receiving sample data without causing discontinuity in the received sample data even when a number of pieces of sample data to be transmitted by a transmitting terminal does not coincide with that of sample data to be received by a receiving terminal.

[0019] According to a first aspect of the present invention, there is provided a signal receiving circuit including:

[0020] a converting circuit to perform computations on a plurality of pieces of first sample data contained in n₁ (n₁ is a natural number) pieces of first sample data sequentially input and to sequentially produce n₁ (n₂ is a natural number) pieces of second sample data in response to a clock signal;

[0021] a receiving circuit to sequentially receive the n₂ pieces of the second sample data in response to the clock signal; and

[0022] wherein the number n₂ is determined by the clock signal.

[0023] With the above configuration, discontinuity can be prevented from occurring in the n₂ pieces of the second sample data.

[0024] In the foregoing, a preferable mode is one wherein the converting circuit outputs, in accordance with a difference between a number of the first sample data input to the converting circuit and a number of the second sample data received by the receiving circuit, one piece of the first sample data existing backward, contained in the plurality of pieces of the first sample data, as one piece of the second sample data contained in the n₂ pieces of the second sample data, in a delayed manner.

[0025] With the above configuration, the second sample data properly expressing the first sample data can be produced.

[0026] Also, a preferable mode is one wherein the one piece of the second sample data is one piece of the first sample data existing backward by N pieces of sample data and output in a delayed manner and wherein the value N is a positive number being not less than 0 (zero) and is able to be a value other than an integer.

[0027] With the above configuration, the n₂ pieces of the second sample data can be changed continuously.

[0028] Also, a preferable mode is one wherein the converting circuit has a controller used to produce a control signal in response to the number n₁ and the number n₂ and a computational section used to perform a computation on the plurality of pieces of the first sample data in response to the control signal and to produce the n₂ pieces of the second sample data.

[0029] Also, a preferable mode is one wherein the computational section has a plurality of storing sections each being used to store one different piece of the first sample data contained in the plurality of pieces of the first sample data, a plurality of multipliers each being used to output a computational result obtained by multiplying one different piece of the first sample data by a predetermined coefficient Aj and an adder used to do addition of the computational result and to output the computational result as one piece of second sample data contained in the plurality of pieces of the second sample data.

[0030] Also, a preferable mode is one wherein the predetermined coefficient A_(j) used in the plurality of the multipliers is obtained by an equation: ${Aj} = {\frac{{\sin \left( {k + \delta - j} \right)}\pi}{\left( {k + \delta - j} \right)\pi}{h\left( {k + \delta - j} \right)}}$

[0031] where “n” is a number of multipliers making up the plurality of pieces of the multipliers, “j” is an integer from 1 to n, “k” is a natural number being larger than 1 and being smaller than “n” and “h (i)” represents a window function. The value “δ” is determined in response to the control signal.

[0032] Also, a preferable mode is one wherein the value “h (i)” is a Hamming function.

[0033] With the above configuration, since the predetermined coefficient A_(j) has the window function as a factor, at a frequency being not more than a cutoff frequency, a gain of the converting circuit is not influenced by frequency and therefore the “h (i)” can be the Hamming factor.

[0034] Also, a preferable mode is one wherein the predetermined coefficient A_(j) used in the plurality of the multipliers is obtained by an equation: ${Aj} = \frac{\sin \quad \left( {k + \delta - j} \right)\pi}{\left( {k + \delta - j} \right)\pi}$

[0035] where “n” is a number of multipliers making up the plurality of the multipliers, “j” is an integer from 1 to n and “k” is a natural number being larger than 1 and being smaller than “n”. The value “δ” is determined in response to the control signal.

[0036] Also, a preferable mode is one wherein, every time the receiving section receives the second sample data, a difference (N₁−N₂) between a number N₁ of the first sample data to be input to the converting circuit for a specified period and a number N₂ of the second sample data to be received by the receiving section for the specified period is added to the value “δ” and, every time the receiving section receives the second sample data, the value “δ” comes close to 0 (zero) by a specified value.

[0037] With the above configuration, the number of sample data by which the first sample data is output in a delayed manner is changed continuously.

[0038] According to a second aspect of the present invention, there is provided a digital voice signal receiving circuit provided with signal receiving circuits as stated above, wherein n, pieces of first sample data and n₂ pieces of second sample data are digital voice data.

[0039] With the above configuration, discontinuity of received digital voice data is held down, thus enabling elimination of noise.

[0040] According to a third aspect of the present invention, there is provided a method for receiving signals including:

[0041] a step of performing sequential computations on a plurality of pieces of first sample data contained in n₁ (n₁ is a natural number) pieces of first sample data;

[0042] a step of producing n₂ (n₂ is a natural number) pieces of second sample data in response to a clock signal; and

[0043] a step of sequentially receiving the second sample data in response to the clock signal.

[0044] In the foregoing, a preferable mode is one wherein the step of producing the n₂ pieces of second sample data includes a step of outputting, in accordance with a difference between a number of the first sample data and a number of the second sample data to be received by a receiving section, one piece of the first sample data existing backward, contained in the plurality of pieces of the first sample data, as one piece of the second sample data contained in the n₂ pieces of the second sample data, in a delayed manner.

[0045] With the above configuration, discontinuity in the n₂ pieces of the second sample data is difficult to occur.

[0046] Also, a preferable mode is one wherein the one piece of the second sample data is the one piece of the first sample data existing backward by N pieces of sample data and output in a delayed manner and wherein the value N is a positive number being not less than 0 (zero) and is able to be a value other than an integer.

[0047] Also, a preferable mode is one wherein toe step of producing the n₂ pieces of second sample data includes a step of using a value S calculated by an equation: $S = {\sum\limits_{j = 1}^{n}{\frac{{\sin \left( {k + \delta - j} \right)}\pi}{\left( {k + \delta - j} \right)\pi}{Dj}}}$

[0048] as one piece of the second sample data contained in the n₂ pieces of second sample data, where each of D₁, D₂, . . . , D_(n) (n is a natural number being not less than 2) is a value of each of the plurality of pieces of the first sample data, “j” is an integer from 1 to n, “k” is a natural number being larger than 1 and smaller than n and wherein the step of producing the n₂ pieces of second sample data includes a step of calibrating a value “δ” in accordance with a difference between the number n₁ and the number n₂.

[0049] Also, a preferable mode is one wherein the step of producing the n₂ pieces of second sample data includes a step of using a value S calculated by an equation: $S = {\sum\limits_{j = 1}^{n}{\frac{{\sin \left( {k + \delta - j} \right)}\pi}{\left( {k + \delta - j} \right)\pi}{h\left( {k + \delta - j} \right)}{Dj}}}$

[0050] as one piece of the second sample data contained in the n₂ pieces of the second sample data, where each of D₁, D₂, . . . , D_(n) (n is a natural number being not less than 2) is a value of each of the plurality of pieces of the first sample data, “j” is an integer from 1 to n, “k” is a natural number being larger than 1 and smaller than n and “h (i)” represents a window function and wherein the step of producing the n₂ pieces of second sample data includes a step of calibrating a value “δ” in accordance with a difference between the number n₁ and the number n₂.

[0051] With the above configuration, since the one piece of the second sample data is produced using the window function “h (i)” at a frequency being not more than a cutoff frequency, a gain of the converting circuit is not influenced by frequency

[0052] Also, a preferable mode is one wherein the value “h (i)” is a Hamming function.

[0053] Furthermore, a preferable mode is one wherein, every time the receiving section receives the second sample data, a difference (N₁−N₂) between a number N₁ of the first sample data to be input to the converting circuit for a specified period and a number N₂ of the second sample data to be received by the receiving section for the specified period is added to the value “δ” and, every time the receiving section receives the second sample data, the value “δ” comes close to 0 (zero) by a specified value.

[0054] According to a fourth aspect of the present invention, there is provided a method for receiving digital voice signals using methods for receiving signals stated above, wherein n₁ pieces of first sample data and n₂ pieces of second sample data are digital data which shows a voice.

[0055] With the above aspects, even if the number of the sample data to be transmitted from the transmitting terminal does not coincide with that of the sample data to be received by the receiving terminal, the sample data can be received without the occurrence of the discontinuity in received sample data.

BRIEF DESCRIPTION OF THE DRAWINGS

[0056] The above and other objects, advantages and features of the present invention will be more apparent from the following description taken in conjunction with the accompanying drawings in which:

[0057]FIG. 1 is a schematic block diagram showing configurations of a signal receiving circuit according to an embodiment of the present invention;

[0058]FIG. 2A is a diagrams showing transmitting sample data used in the signal receiving circuit according to the embodiment of the present invention;

[0059]FIG. 2B is a diagram showing clock pulses and receiving sample data used in the signal receiving circuit according to the embodiment of the present invention;

[0060]FIG. 3 is a diagram showing values of a coefficient A_(j) (q) used when δ(q)=0, employed in the signal receiving circuit according to the embodiment of the present invention;

[0061]FIG. 4 is a diagram showing values of a coefficient A_(j) (q) used when δ(q)=1, employed in the signal receiving circuit according to the embodiment of the present invention;

[0062]FIG. 5 is a diagram showing values of a coefficient A_(j) (q) used when δ(q)=0.25, employed in the signal receiving circuit according to the embodiment of the present invention;

[0063]FIG. 6 is a diagram showing operations of the signal receiving circuit according to the embodiment of the present invention; and

[0064]FIG. 7 is a schematic diagram showing configurations of a conventional voice signal receiving circuit.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT

[0065] Best modes of carrying out the present invention will be described in further detail using various embodiments with reference to the accompanying drawings.

Embodiment

[0066]FIG. 1 is a schematic block diagram showing configurations of a signal receiving circuit according to an embodiment of the present invention. The signal receiving circuit of the embodiment is used as the signal receiving circuit to receive a digital voice signal. As shown in FIG. 1, the signal receiving circuit is provided with a filter 1 to which a transmitting signal “a” is input.

[0067] The filter 1 is an r-th order FIR (Finite Impulse Response) filter. The “r” is a natural number being not less than three. In this embodiment, the “r”=9. The filter 1 has a shift register 2. The transmitting signal “a” is input to the shift register 2.

[0068] The shift register 2 includes registers 2-1 to 2-9. To an input terminal of the register 2-1 is input the transmitting signal “a”. An output of the register 2-1 is input to the register 2-2. An output of the register 2-2 is input to the register 2-3. Similarly, outputs of the register “2-(i-1)” are input to the register “2-i”. The “i” is a natural number being not less than two and being not more than nine.

[0069] The shift register 2 is connected to a multiplier 3. The multiplier 3 includes multipliers 3-1 to 3-9. An output of the register 2-1 is input to the multiplier 3-1. An output of the register 2-2 is input to the multiplier 3-2. Similarly, outputs of the registers 2-j are input to the multipliers 3-j. The “j” is a natural number being not more than nine. Outputs of the multipliers 3-1 to 3-9 are input to an adder 4. The adder 4 outputs a receiving signal “c”.

[0070] The receiving signal “c” is input to a D/A (Digital/Analog) converter 5. To the D/A converter 5 is input a receiving clock signal “d”. The D/A converter 5 is connected to a speaker 6.

[0071] The signal receiving circuit of the embodiment further includes a controller 7. The controller 7 has a counter 8 and a control signal output section 9. To the counter 8 are input both the transmitting signal “a” and the receiving clock signal “d”. The counter 8 is connected to the control signal output section 9.

[0072] Next, operations of the signal receiving circuit of the embodiment will be described below. The transmitting signal “a” is input to the filter 1 and to the controller 7. The transmitting signal “a” is the digital voice signal. The transmitting signal “a”, as shown in FIG. 2A, includes transmitting sample data x (0) x(1), . . . , x(p), . . . . The “p” is an arbitrary integer being not less than zero.

[0073] At time t=t0, the transmitting sample data x(0) is input to the filter 1 and the controller 7. At time t=t1, the transmitting sample data x(1) is input to the filter 1 and the controller 7. Similarly, at time=tp, the transmitting sample data x(p) is input to the filter 1 and the controller 7. The time is assumed to be t0<t1< . . . <tp<tp+1< . . . .

[0074] Each of the transmitting sample data x(p) is made up of 16 bits. The “p” is an arbitrary integer being not less than zero. The number of bits making up the transmitting sample data may be other number of bits.

[0075] The filter 1, n response to a control signal “b” produced by the controller 7, converts the transmitting signal “a” to the receiving signal “c”. The filter 1 outputs the receiving signal “c” to the D/A converter 5. The controller 7, in response to the transmitting signal “a” and the receiving clock signal “d”, produces the control signal “b”.

[0076] A process of producing the control signal “b” will be described below. The transmitting signal “a” is input to the counter 8. The counter 8 holds a counter value “K”. The counter 8, every time when each of the transmitting sample data x(p) is input, increases the counter value “K” by one. The “p” is an arbitrary integer being not less than zero.

[0077] Moreover, to the counter 8 is input the receiving clock signal “d”. As shown in FIG. 2B, the receiving clock signal “d” has clock pulses P₀, P₁, P₂, . . . , Pq, . . . . The “q” is an arbitrary integer being not less than zero. The clock P₀ is input to the counter 8 at time t=t0′. Let it be assumed here that t0<t0′.

[0078] The clock pulse P₁ is input to the counter 8 at time t=t1′. Similarly, the clock pulse P_(q) is input to the counter 8 at time t=tq′.

[0079] The counter 8, every time when any one of the clock pulses P_(q) is input, decreases the counter value K by one. The “q” is an arbitrary integer being not less than zero. The counter value K obtained after the counter value has been decreased by one due to inputting of the clock pulse P₀ becomes a control value δ(0). Similarly, the counter value K obtained after the counter value has been decreased by one due to inputting of the clock pulse P_(q) becomes a control value δ(q). The control value δ(q) is transferred to the control signal output section 9 via a counter signal “f”.

[0080] To the control signal output section 8 is input the receiving clock signal “d”. The time when the clock pulse P_(q) contained in the receiving clock signal “d” is input to the control signal output section q is substantially the same as the clock pulse P_(q) is input to the counter 8.

[0081] The control signal output section 9, when the clock pulse P₀ is input, captures the control value δ(0) . Similarly, the control signal output section 9, every time when the clock pulse P_(q) is input, captures the control value δ(q) . The “q” is an arbitrary integer being not less than zero. The control signal output section 9, when the clock pulse P_(q) is input, transfers the control value δ(q) to the filter 1 via the control signal “b”.

[0082] The control signal output section 9, after having transferred the control value δ(q) to the filter 1 via the control signal “b” further outputs a counter control signal “g” to the counter 8. The counter control signal “g” is a signal used to instruct the counter a to increase the counter value K by Δx or to decrease the counter value K by Δx. It is assumed that 0<Δ×<0.5.

[0083] In response to the counter control signal “g” the counter 8 performs the following operations. That is, when −Km≦δ(q)≦Km (“q” is an arbitrary integer being not less than zero), the counter 8 holds the counter value K as it is. The “Km” is an integer being not less than zero. When δ(q)>Km, the counter 8 decreases the counter value K by Δx. When δ(q)>−Km, the counter 8 increases the counter value K by Δx. The Δx is not an integer. Therefore, the counter value K can take a value being not an integer. The result from the increase of the counter value K by Δx or the decrease by Δx is reflected in the control value δ(q+1) which is transferred by the control signal “b” when the clock pulse P_(q−1) is input. Since the counter value K held by the counter 8 can take a value other than an integer, the control value δ(q+1) also can take a value other than the integer (“q” is an integer being not less than zero).

[0084] Processes of producing the control signal “b” are described above. Then, processes in which the transmitting signal “a” is converted into the receiving signal “c” by the filter 1 in response to the control signal “b” will be explained.

[0085] The transmitting signal “a” is input to the register 2-1 included in the filter 1. The transmitting signal “a” includes transmitting sample data x(0), x(1), . . . , x(p), . . . .

[0086] Each of the registers 2-1 to 2-9 has each of data D₁ to D₉. Each of the D₁ to D₉ is any one of the transmitting sample data x(0), x(1), . . . , x(p), . . . . The data D₁ to D₉ are determined in the following manner.

[0087] When the transmitting sample data x(p) is input to the register 2-1, the register 2-1 captures and stores the data x(p) The “p” is an integer being not less than zero. The data D₁ becomes x(p) . At this point, The data D₂ held by the register 2-2 becomes x(p−1). The data D₃ held by the register 2-3 becomes x(p-2).

[0088] Similarly, when the transmitting sample data x(p) is input to the register 2-1, data Dj held by the register 2-1 becomes x(p−{j−1}) . The “j” is a natural number being not more than nine. That is, when the transmitting sample data x(p) is input to the register 2-1, the register 2-i, immediate before the transmitting sample date x(p) is input to the register 2-1, captures and stores data held by the register 2-(i−1).

[0089] The register 2-1 outputs its holding data D₁ to the multiplier 3-1. The register 2-2 outputs its holding data D₂ to the multiplier 3-2. Similarly, the register 2-j outputs its holding data D_(j) to the multiplier 3-j.

[0090] The multipliers 3-1 to 3-9 perform computations in response to the control signal “b”. The multiplier 3-1 multiplies the data D₁ by a coefficient A₁(q) and outputs the result to the adder 4. The multiplier 3-2 multiplies the data D₂ by a coefficient A₂(q) and outputs the result to the adder 4. Similarly, the multiplier 3-j multiplies the data D_(j) by a coefficient A_(j) (q).

[0091] The coefficients A₁(q) to A₉(q) used for the multiplication by the multipliers 3-1 to 3-9 are determined by the control value δ(q) transferred by the multipliers 3-1 to 3-9. The coefficients A₁(q) to A₉(q) are obtained by an equation: $\begin{matrix} {{{Aj}(q)} = {\frac{\sin \quad \left. \left( {k + {\delta (q)} - j} \right. \right\} \pi}{\left\{ {k + {\delta (q)} - j} \right\} \pi}{h\left( {k + {\delta (q)} - j} \right)}}} & (1) \end{matrix}$

[0092] where “k” is a natural number. In the embodiment, k=5.

[0093] The h(i) represents a window function. It may be a Hamming function. That is, the window function is given by an equation:

h(i)=0.54−0.46 cos(2π/9)  (2)

[0094] Moreover, the window function “h(i)” may be one other than the Hamming function. By using the Hamming function as the window function “h(i)”, it is made possible that, at a frequency being not more than a cutoff frequency, a gain of the filter 1 is not influenced by frequencies. Moreover, the window function “h(i)” may be one.

[0095] The control value δ(q) is renewed every time the clock pulse P_(q) is input to the counter 8. Therefore, the coefficients A₁ (q) to A₉ (q) are also renewed every time the clock pulse P_(q) is input to the counter 8. The “q” is an arbitrary integer being not less than zero.

[0096] The adder 4 does the sum of computed results of each of the multipliers 3-1 to 3-9 and uses it as receiving sample data “y”. The coefficients A₁(q) to A₉(q) that the multipliers 3-1 to 3-9 use for the multiplication are renewed every time the clock pulse P_(q) is input to the counter 8. The receiving sample data “y” is also renewed every time the clock pulse P₀ to P_(m) is input to the counter 8. The receiving sample data “y” which is produced when the clock pulse P_(q) is input to the counter 8 is hereinafter called “receiving sample data y(q)”. The receiving sample data y(q) is given by the following equation: $\begin{matrix} {{y(q)} = {\sum\limits_{j = 1}^{9}{{{Aj}(q)}{{Dj}(q)}}}} & (3) \end{matrix}$

[0097] where the “D₃(q)” represents data which is held by the register 2-j the clock pulse P_(q) is input to the counter 8. Here, of

[0098] the transmitting sample data x (p) input before the clock pulse P_(q) has been input to the counter 8, transmitting sample data input to the register 2-1 the most immediately before the inputting is called the data x(p′). At this point, D₁(q)=x(p′). D₂(q)=x(p′−1). Similarly, D_(j) (q)=x(p′−{j−1}). That is, the following equation is obtained: $\begin{matrix} {{y(q)} = {\sum\limits_{j = 1}^{9}{{{Aj}(q)}{x\left( {p^{\prime} - \left( {j - 1} \right)} \right)}}}} & (4) \end{matrix}$

[0099] The adder 4 transfers the receiving sample data y(q) to the D/A converter 5 via the receiving signal c.

[0100] The receiving signal “c” Is input to the D/A converter 5. To the D/A converter 5 is further Input a receiving clock signal “d”. The D/A converter 5 samples the receiving signal “c” in response to the receiving clock signal “d”.

[0101] When the clock pulse P₀ is input to the D/A converter 5, the D/A converter 5 captures receiving sample data y(0). Similarly, when the clock pulse P_(q) (q is an arbitrary integer being not less than zero) is input to the D/A converter 5, the D/A converter 5 captures receiving sample data y(q) . The D/A converter 5 receives the receiving sample data y every time, it receives one clock pulse.

[0102] The D/A converter 5 produces an analog voice signal “e” using the receiving sample data y (q) contained in the captured receiving signal “c”. The D/A converter 5 outputs an analog voice signal “e” to the speaker 6. The speaker 6 outputs a voice in response to the analog voice signal “e”.

[0103] A main function of the signal receiving circuit of the embodiment is that the filter 1 produces the receiving sample data y(q) by using the above equation (4). Computations by the filter 1 using the equation (4) will be described below.

[0104] The coefficient A_(j) (q) used for the multiplication 4 the multipliers 3-1 to 3-9 has a window function h (k+δ(q)−j) as a factor. The window function is related only to frequency characteristics. The window function has nothing to do with an essential operation of the filter 1. To simplify the explanation, let it be assumed that the window function h (k+δ(q)−j)=1.

[0105] A condition occurring when δ(q)=0 will be described. FIG. 3 is a diagram showing values of the coefficient A_(j) (q) used when δ(q)=0. In this case, the window function h (i)=1 and k=5. When j≠k, A_(j) (q)=0. When j=k, A_(j) (q)=1.

[0106] The equation y(q)=x(p′−k−1)), that is, the equation y(q)=x(p′−4) can be derived from the equation (4). The following is meant by this equation:

[0107] Here let it be assumed that, while δ(q)=0, the transmitting sample data x(p−4), x(p−3), x(p−2), x(p−1) and x(p) are input sequentially and, immediately after the inputting of the sample data, the clock pulse P_(q) is input to the counter 8 and further p′=p. At this point, the result is that y(q)=x(p−4).

[0108] That is, the filter 1 outputs the transmitting sample data x(p−4) existing backward by four pieces of sample data as the receiving sample data y(q), in a delayed manner. Thus, when δ(q)=0, the filer 1 outputs the transmitting sample data (k−1) existing backward by (k−1) pieces of sample data as the receiving sample data y(q), in a delayed manner.

[0109] When δ(q)=0, each of the coefficients A_(j) (q) (“j” is a natural number being one to nine) is determined so that the transmitting sample data x(p) is output by (k−1) pieces of the sample data in a delayed manner. The filter 1 performs computations of the transmitting sample data using the registers 2-1 to 2-2, multipliers 3-1 to 3-9 and adder 4. The result of the computation causes the transmitting sample data existing backward by (k−1) pieces of the sample data to be output in a delayed manner.

[0110]FIG. 4 is a diagram showing values of the coefficient A_(j) (q) used when δ(q)=1. Here, the window function h (i)=1 and k=5. In the case the δ(q) being one, if j≠k+1 (=6), A_(j) (q)=0. When j=k+1 (=6), A_(j) (q)=1. The equation y(q)=x(P′−5) can be derived from the equation (4). That is, when δ(q)=1, the filter 1 outputs the transmitting sample data x(p) existing backward by five pieces of the sample data as the receiving sample data y(q), in a delayed manner. At this point, each of the coefficients A_(j)(q) (“j” is a natural number being one to nine) is determined so that the transmitting sample data x (p) existing backward by five pieces of the sample data is output in a delayed manner.

[0111] The above theory can be extended to a case where δ(q) is not an integer. FIG. 5 a diagram showing values of the coefficient A_(j) (q) used when δ(q)=0.25. Here, k=5. At this point, each of the coefficients A_(j) (q) (“j” is a natural number being one to nine) is determined so that the transmitting sample data x(p) existing backward by substantially 4.25 pieces of the sample data is output in a delayed manner. The filter 1 outputs the transmitting sample data x(p) existing backward by substantially 4.25 pieces of samples as the receiving sample data y(q) in a delayed manner.

[0112] Thus, as described above, the filter 1 serves as a delaying unit adapted to output the transmitting sample data x(p) existing backward by “(k−1)+δ(q)” pieces of the sample data in a delayed manner. When δ(q) is not an integer, the filter 1 outputs the transmitting sample data x(p) existing backward by (k−1)+δ(q) pieces of the sample data in a delayed manner.

[0113] The number of delayed samples (k−1)+δ(q) for the outputting by the filter 1 is calibrated according to the number of pieces of the transmitting sample data x(p) to be input to the counter 8 and to the number of the clock pulse P_(q) contained in the receiving clock signal “d” to be input to the counter 8.

[0114] Next, calibration of the number of sample data (k−1)+δ(q) by which the filter 1 outputs in a delayed manner will be described below.

[0115] In the embodiment, let it be assumed that k=5, Km=0, h (i)=1 and Δx=0.2. In the signal receiving circuit of the embodiment, after one piece of transmitting sample data is input to the filter 1, one clock pulse is input to the D/A converter 5 and one piece of receiving sample data is received.

[0116] In the signal receiving circuit, when one piece of the transmitting sample data receives one clock pulse, the number of pieces of delayed samples in the filter 1 is adapted to be four. That is, the signal receiving circuit is so configured that, when the clock pulse P_(n) is input to the counter 8 immediately after the transmitting sample data x(m) has been Input to the counter 8, the receiving sample data y(n)=x(m−4), y(n+1)=x(m−3), y(n+2)=x(m−2), . . . , y(n+7)=x(m+3). Here, m≧4.

[0117] However, let it be assumed that a clock pulse P_(n+1) has been lost due to some reasons. The clock pulse P_(n+1) to be corresponded to a transmitting sample data x(m+1) is not input. At this time, the receiving sample data y(n+1) is not produced. Operations of the signal receiving circuit in this situation will be explained by referring to FIG. 6. Let the counter value K be zero hen time t<t_(m).

[0118] In the case of t_(m)≦t<t_(m+1):

[0119] At the time t_(m), the transmitting sample data x(m) is input to the filter 1 and the counter 8. The counter value K increments by one. K becomes one. Then, at the time t_(n′), the clock pulse P_(n) is input to the counter 8. The counter value K decrements by one. K becomes 0. δ(n) becomes zero.

[0120] At this point, the number of delayed samples “δ(n)+4” in the filter 1 is fore. As a result, y(n)=x(m−4). The counter control signal “g” is input to the counter 8. It is neither that δ(n)>Km, nor that δ(n)<Km. The counter value K remains as it is.

[0121] In the case of t_(m+1)≦t<t_(m+3):

[0122] At the time t_(m+1), the transmitting sample data x(m+1) is input to the filter 1 and to the counter 8. The counter value increments by one. K becomes one. The clock pulse P_(m+1) to be input following the transmitting sample data x(m+1) is not input to the filter 1 and to the counter 8. The data y(n+1) is not produced.

[0123] At the time t_(m+1), the transmitting sample data x(m+2) is input to the filter 1 and to the counter 8. The counter value K increments by one. K becomes two. Then, at the time t_(n+2′), the clock pulse P_(n+2) is input to the counter 8. The counter value K decrements by one. K becomes one. δ(n+2) becomes one. At this point, the number of delayed samples in the filter 1 “δ(n+2)+4”=5. As a result, y(n+2)=x(m=3).

[0124] The counter control signal “g” is input to the counter 8. Here, δ(n+2)>Km (=0). At the time t_(n+2″), the counter value K decrements by Δ x. K becomes 0.8.

[0125] In the case of t_(m+3)≦t<t<t_(m+4):

[0126] At the time t_(m+3), the transmitting sample data x(m+3) is input to the filter 1 and to the counter 8. The counter value K increments by one. K becomes 1.8. Then, at the time t_(n+3′), the clock pulse P_(n+3) is input to the counter 8. The counter value K decrements by one. K becomes 0.8. As a result, δ(n+3)=0.8.

[0127] At this point, the substantial number of the delayed samples in the filter 1 “δ(n+3)+4”=4.8. The receiving sample data y(n+3) becomes practically data being equivalent to the data x(m−1.8). In FIG. 6, when the receiving sample data y(n+3) is data being substantially x(m−1.8), it is expressed as y(n+3)≈x(m−1.8).

[0128] The counter control signal “g” is input to the counter 8. Here, δ(n+3)>Km (=0). At the time t_(n+3), the counter value K decrements by Δ x. K becomes 0.6.

[0129] In the case of t_(m+4)≦t<t_(m+5):

[0130] At the time t_(m+4), the transmitting sample data x(m+4) is input to the filter 1 and the counter 8. K becomes 1.6. Then, at the time t_(m+4)′, the clock pulse P_(n+4) is input to the counter 8. K becomes 0.6.

[0131] At this point, the substantial number of the delayed samples in the filter 1 “δ(n+4)+4”=4.6. The receiving sample data y(n+4) becomes practically data being equivalent to the data x(m−0.6).

[0132] Here, δ(n+4)>Km (=0). At the time t_(n+4″), the counter value K decrements by Δ x. K becomes 0.4.

[0133] In the case of t_(m+5)≦t<t_(m+6):

[0134] At the time t_(m+5), the transmitting sample data x(m+5) is input to the filter 1 and the counter 8. K becomes 1.4. Then, at the time t_(n+5′), the clock pulse P_(n+5) is input to the counter 8. K becomes 0.4.

[0135] At this point, the substantial number or the delayed samples in the filter 1 “δ(n+5)+4”=4.4. The receiving sample data y(n+5) becomes practically data being equivalent to the data x(m+0.6).

[0136] Here, δ(n+5)>Km (=0). At the t_(n+5″), the counter value K decrements by Δ x. K becomes 0.2.

[0137] In the case of t_(m+6)≦t<t_(m+7):

[0138] At the time t_(m+6), the transmitting sample data x(m+6) is input to the filter 1 and the counter 8. K becomes 1.2. Then, at the time t_(n+6′), the clock pulse P_(n+6) is input to the counter 8. K becomes 0.2.

[0139] At this point, the substantial number of the delayed samples in the filter 1 “δ(n+6)+4”=4.2. The receiving sample data y(n+6) becomes practically data being equivalent to the data x(m+1.8).

[0140] Here, δ(n+6)>Km (=0). At the time t_(n+6″), the counter value K decrements by Δ x. K becomes zero.

[0141] In the case of t≧t_(m−7):

[0142] At the time t_(m+7), the transmitting sample data x(m+7) is input to the filter 1 and the counter 8. K becomes 1.0. Then, at the time t_(n+7′), the clock pulse P_(n+7) is input to the counter 8. K becomes zero.

[0143] At this point, the number of the delayed samples in the filter “δ(n+7)+4”=4. The receiving sample data y(n+7)=x(m+3). The receiving sample data y(n+7) becomes the same as in the case where the clock pulse P_(n+1) has not been lost.

[0144] In the signal receiving circuit of the embodiment, when the number of pieces of the transmitting sample data to be input to the filter 1 is equal to that of the clock pulses to be input to the D/A converter 5, the transmitting sample data is output in a delayed manner by four samples.

[0145] Moreover, the signal receiving circuit of the embodiment, when detecting that the number of the transmitting samples to be input to the filter 1 is larger by one than that of the clock pulse to be input to the D/A converter 5, substantially changes the number of the delayed samples in the filter 1 while decreasing it from five to four by Δ x(=0.2). Thus, the receiving sample data y(n), y(n+1), are continuously changed. When the transmitting sample data x(m), x(m+1), . . . and the receiving sample data y(n), y(n+1) are digital signals, the analog voice signal “e” reproduced by the D/A converter 5 is not discontinuous.

[0146] Similarly, the signal receiving circuit of the embodiment, when detecting that the number of the transmitting sample to be input to the filter 1 is smaller by one than that of the clock pulse to be input to the D/A converter 5, substantially changes the number or the delayed samples in the filter 1 while increasing it from three to four by Δ x(=0.2). Thus, the receiving sample data y(n), y(n+1), are continuously changed.

[0147] The signal receiving circuit of the embodiment, when detecting that the number of pieces of the transmitting sample data x(p) to be input to the counter 8 differs by one from that of the clock pulse P_(q) contained in the receiving clock signal “d” to be input to the counter 8, changes the number of the delayed samples in the filter 1 by Δ x while (1/Δ x) pieces of the clock pulses P_(q) are input.

[0148] Here, let it be assumed that the sampling frequency of the transmitting terminal differs slightly from those of the receiving terminal. At this time, the number of pieces, of the transmitting sample data x(p) to be input to the counter 8 differs, at all times, from that of the clock pulses P_(q) contained in the receiving clock signal “d” to be input to the counter 8.

[0149] Here, let it be assumed that the number required for causing the difference between the nature of the transmitting sample data x(p) to be input to the counter 8 and the number of the clock pulse P_(q) contained in the receiving clock signal “d” to be input to the counter 8 to be one, is defined to be “nP”. In the signal receiving circuit of the embodiment, so long as nP>1/Δ x, the receiving sample data y(n), y(n+1), . . . can be continuously changed.

[0150] For example, let it be assumedly that, when signals are transmitted or received at the sampling frequency of 16 kHz, a difference of 4 Hz occurs between the sampling frequency of the transmitting terminal and of the receiving terminal. If so, every time the receiving terminal receives signal about 400 times, the number of pieces of the transmigrating sample data to be transmitted by the transmitting terminal differs by one from the number of pieces of the receiving sample data to be received by the receiving terminal. At this pliant, so long as 400>(1/Δ x), that is, Δ x>0.0025, the signal receiving circuit of the embodiments can change continuously the receiving sample data y(n), y(n+1), . . . .

[0151] The value Δ x is preferably as small as possible within a range meeting a condition that np>1/Δ x. The reason is that the receiving sample data y(n), y(n+1) can be continuously changed. Specifically, for the digital voice communications in which signals are transmitted or received at the sampling frequency of 16 kHz, the value “1/Δ x” is preferably about 256.

[0152] It is apparent that the present invention is not limited to the above embodiments but may be changed and modified without departing front the scope and spirit of the invention. For example, in the above embodiment, the signal receiving circuit is used as the signal receiving circuit used for receiving the digital voice signal, however, it may be used as signal receiving circuits other than the circuit for the digital voice signal and it nay be used as a signal receiving circuit to receive digital image signals between communication terminals being not in sync with each other. Moreover, the signaled receiving circuited of the embodiment may be used as a signal receiving circuit in which, though complete reproduction of a transmitted signal is not required, continuity in signal waveforms and on a time axis is required. 

What is claimed is:
 1. A signal receiving circuits comprising: a converting circuit to perform computations on a plurality of pieces of first sample data container in n₁ (n₁ is a natural number) pieces of first sample data sequentially input and to sequentially produce n₂ (n₂ is a natural number) pieces of second sample data in response to a clock signal; a receiving circuit to sequentially receive said n₂ pieces of said second sample data in response to said clock signal; and wherein said number n₂ is determined by said clock signal.
 2. The signal receiving circuit according to claim 1 , wherein said converting circuit outputs, in accordance with a difference between a number of said first sample data input to said converting circuit and a number of said second sample data received by said receiving circuit, one piece of said first sample data existing backward, contained in said plurality of pieces of said first sample data, as one piece of said second sample data contained in said n₃ pieces of said second sample data, in a delayed manner.
 3. The signal receiving circuit according to claim 2 , wherein said one piece of said second sample data is said first sample data existing backward by N pieces of sample data and output in a delayed manner and wherein said value N is a positive number being not less than 0 (zero) and is able to be a value other than an integer.
 4. The signal receiving circuit according to claim 1 , wherein said converting circuit has a controller used to produce a control signal in response to said number n₁ pieces and said number n₂ pieces and a computational section used to perform a computation on said plurality of pieces of said first sample data in response to said control signal and to produce said n₂ pieces of said second sample data.
 5. The signal receiving circuit according to claim 4 , wherein said computational section has a plurality of storing sections each being used to store one different piece of said first sample data contained in said plurality of pieces of said first sample data, a plurality of multipliers each being used to output a computational result obtained by multiplying one different piece of said first sample data by a predetermined coefficient A_(j) and an adder used to do addition of said computational result and to output said computational result as one piece of said second sample data contained in said plurality of pieces of said second sample data.
 6. The signal receiving circuit according to claim 5 , wherein said predetermined coefficient A_(j) used in said plurality of said multipliers is obtained by an equation; ${{Aj}(q)} = {\frac{\sin \quad \left. \left( {k + \delta - j} \right. \right\} \pi}{\left\{ {k + \delta - j} \right\} \pi}{h\left( {k + \delta - j} \right)}}$

where “n” is a number of multipliers making up said plurality of said multipliers, said “j” is an integer from 1 to said “n”, “k” is a natural number being larger than 1 and being smaller than said “n”, and “h (i)” represents a window function. Said value “δ” is determined in response to said control signal.
 7. The signal receiving circuit according to claim 6 , wherein said “h (i)” is a Hamming function.
 8. The signal receiving circuit according to claim 5 , wherein said predetermined coefficient A_(j) used in said plurality of said multipliers is obtained by an equation: ${Aj} = \frac{\sin \quad \left( {k + \delta - j} \right)\pi}{\left( {k + \delta - j} \right)\pi}$

where “n” is a number of multipliers making up said plurality of said multipliers, “j” is an integer from 1 to “n” and “k” is a natural number being larger than 1 and being smaller than “n”. Said value “δ” is determined in response to said control signal.
 9. The signal receiving circuit according to claim 6 , wherein, every time said receiving section receives said second sample data, a difference (N₁−N₂) between a number N₁ of said first sample data to be input to said converting circuit for a specified period and a number N₂ of said second sample data to be received by said receiving section for said specified period is added to said value “δ” and, every time said receiving section receives said second sample data, said value “67 ” comes close to 0 (zero) by a specified value.
 10. The signal receiving circuit according to claim 8 , wherein, every time said receiving section receives said second sample data, a difference (N₁−N₂) between a number N₁ of said first sample data to be input to said converting circuit for a specified period and a number N₂ of said second sample data to be received by said receiving section for said specified period is added to said value “δ” and, every time said receiving section receives said second sample data, said value “δ” comes close to 0 (zero) by a specified value.
 11. The signal receiving circuit according to claim 1 , wherein said n₁ pieces of said first sample data and said n₂ pieces of said second sample data are digital voice data.
 12. A method for receiving signals comprising: a step of performing sequential computations on a plurality of pieces of first sample data contained in n₁ (n₁ is a natural number) pieces of first sample data; a step of producing n₂ (n₂ is a natural number) pieces of second sample data in response to a clock signal; and a step of sequentially receiving said second sample data in response to said clock signal.
 13. The method for receiving signals according to claim 12 , wherein said step of producing said n₂ pieces of second sample data includes a step of outputting, in accordance with a difference between a number of said first sample data and a number of said second sample data to be received by said receiving section, one piece of said first sample data existing backward, contained in said plurality of said first sample data, as one piece of said second sample data contained in said n₂ pieces of said second sample data, in a delayed manner.
 14. The method for receiving signals according to claim 13 , wherein said one piece of said second sample data is said one piece of said first sample data existing backward by N pieces of sample data and output in a delayed manner and wherein said value N is a positive number being not less than 0 (zero) and is able to be a value other than an integer.
 15. The method for receiving signals according to claim 12 , wherein said step of producing said n₃ pieces of second sample data Includes a step of using a value S calculated by an equation: $S = {\sum\limits_{j = 1}^{n}{\frac{{\sin \left( {k + \delta - j} \right)}\pi}{\left( {k + \delta - j} \right)\pi}{Dj}}}$

as one piece of said second sample data contained in said n₂ pieces of said second sample data, where each of D₁, D₂ ₁, . . . , D_(n) (n is a natural number being not less than 2) is a value of each of said plurality of pieces of said first sample data, “j” is an integer from 1 to “n”, “k” is a natural number being larger than 1 and smaller than “n” and wherein said step of producing said n₂ pieces of second sample data includes a step of calibrating said value “δ” in accordance with a difference between said number n₁ and said number n₂.
 16. The method for receiving signals according to claim 12 , wherein said step of producing said n₂ pieces of second sample data includes a step of using a value S calculated by an equation; $S = {\sum\limits_{j = 1}^{n}{\frac{{\sin \left( {k + \delta - j} \right)}\pi}{\left( {k + \delta - j} \right)\pi}{h\left( {k + \delta - j} \right)}{Dj}}}$

as one piece of said second sample data contained in said n₂ pieces of said second sample data, where each of D₁, D₂, . . . , D_(n) (n is a natural number being not less than 2) is a value of each of said plurality of pieces of said first sample data, “j” is an integer from 1 to “n”, “k” is a natural number being larger than 1 and smaller than “n” and “h (i)” represents a window function and wherein said step of producing said n₂ pieces of second sample data includes a step of calibrating said value “δ” in accordance with a difference between said number n₁ and said number n₂.
 17. The method for receiving signals according to claim 16 , wherein said value “h (i)” is a Hamming function.
 18. The method for receiving signals according to claim 15 , wherein, every time said receiving section receives said second sample data, a difference (N₁−N₂) between a number N₁ of said first sample data to be input to said converting circuit for a specified period and a number N₂ of said second sample data to be received by said receiving section for said specified period is added to said value “δ” and, every time said receiving section receives said second sample data, said value “δ” comes close to 0 (zero) by a specified value.
 19. The method for receiving signals according to claim 16 , wherein, every time said receiving section receives said second sample data, a difference (N₁−N₂) between a number N₁ of said first sample data to be input to said converting circuit for a specified period and a number N₂ of said second sample data to be received by said receiving section for said specified period is added to said value “δ” and, every time said receiving section receives said second sample data, said value “δ” comes close to 0 (zero) by a specified value.
 20. The method for receiving signals according to claim 12 , wherein, said n₁ pieces A, said first sample data and said n₂ pieces of said second sample data are digital voice data. 